TPS65140

FEATURES DESCRIPTION

APPLICATIONS

Vin Vo1

Vo3

Power Good

Vo2

Vo4

3.3 V

TPS65140/45

Up to 15 V / 400 mA

Up to 30 V / 20 mA

Up to −12 V / 20 mA

2.7 V to 5.8 V

TPS65140

TPS65145

SLVS497B–SEPTEMBER2003–REVISED MARCH2004 TRIPLE OUTPUT LCD SUPPLY WITH LINEAR REGULATOR AND POWER GOOD

• 2.7-V to5.8-V Input Voltage Range The TPS65140/145offers a compact and small

power supply solution to provide all three voltages • 1.6-MHz Fixed Switching Frequency

required by thin film transistor(TFT)LCD displays.•3Independent Adjustable Outputs

The auxiliary linear regulator controller can be used •Main Output up to15V With<1%Typical to generate a 3.3-V logic power rail for systems Output Voltage Accuracy powered by a5-V supply rail only.

•Negative Output Voltage Down to-12V/20mA The main output Vo1is a1.6-MHz fixed frequency •Positive Output Voltage up to30V/20mA PWM boost converter providing the source drive

voltage for the LCD display.The device is available in •Auxiliary3.3-V Linear Regulator Controller

two versions with different internal switch current •Internal Soft Start

limits to allow the use of a smaller external inductor •Internal Power-On Sequencing when lower output power is required.The TPS65140

has a typical switch current limit of 2.3A and the •Fault Detection of all Outputs

TPS65145has a typical switch current limit of1.37A.•Thermal Shutdown

A fully integrated adjustable charge pump •System Power Good doubler/tripler provides the positive LCD gate drive

voltage.An externally adjustable negative charge •Available in TSSOP-24and QFN-24

pump provides the negative gate drive voltage.Due PowerPAD™Packages

to the high 1.6-MHz switching frequency of the

charge pumps,inexpensive and small220-nF capaci-

tors can be used.

•TFT LCD Displays for Notebooks

Additionally,the TPS65140/145has a system power •TFT LCD Displays for Monitors

good output to indicate when all supply rails are •Portable DVD Players

acceptable.For LCD panels powered by5V,only the •Tablet PCs TPS65140/145has a linear regulator controller using •Car Navigation Systems an external transistor to provide a regulated 3.3V

output for the digital circuits.For maximum safety,the •Industrial Displays

entire device goes into shutdown as soon as one of

the outputs is out of regulation.The device can be

enabled again by toggling the input or the enable

(EN)pin to GND.

Please be aware that an important notice concerning availability,standard warranty,and use in critical applications of Texas

Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.

PowerPAD is a trademark of Texas Instruments.

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Good V I L1

µF

3

V O1 V

TPS65140

TPS65145

SLVS497B–SEPTEMBER2003–REVISED MARCH2004

These devices have limited built-in ESD protection.The leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the MOS gates.

TYPICAL APPLICATION CIRCUIT

ORDERING INFORMATION

(1)The PWP and RGE packages are available taped and reeled.Add an R suffix to the device type(TPS65100PWPR)to order the device

taped and reeled.The PWPR package has quantities of2000devices per reel,and the the RGER package has3000devices per reel.

Without the suffix,the PWP package only,is shipped in tubes with60devices per tube.

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ABSOLUTE MAXIMUM RATINGS

DISSIPATION RATINGS

RECOMMENDED OPERATING CONDITIONS

ELECTRICAL CHARACTERISTICS

TPS65140TPS65145

SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

over operating free-air temperature range (unless otherwise noted)(1)

(1)Stresses beyond those listed under “absolute maximum ratings”may cause permanent damage to the device.These are stress

ratings only,and functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions”is not implied.Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.(2)

All voltage values are with respect to network ground terminal.

(1)

Refer to the application information section for further information.

V in =3.3V,EN =VIN,Vo1=10V,T A =-40°C to 85°C,typical values are at T A =25°C (unless otherwise noted)

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TPS65140TPS65145

SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

ELECTRICAL CHARACTERISTICS (continued)

V in =3.3V,EN =VIN,Vo1=10V,T A =-40°C to 85°C,typical values are at T A =25°C (unless otherwise noted)

DEVICE INFORMATION

EN

ENR COMP

FB2

REF

GND

DRV

C1−

C1+

C2−/MODE C2+

OUT3

F

B

2

R

E

F

G

N

D

D

R

V

C

1

−

C

1

+

V

I

S S

P

G

N

P

G

N

S

U

P

C2−/MODE

C2+

OUT3

FB3

GND

PG

PWP PACKAGE

TOP VIEW RGE PACKAGE

TOP VIEW TPS65140 TPS65145

SLVS497B–SEPTEMBER2003–REVISED MARCH2004 ELECTRICAL CHARACTERISTICS(continued)

V in=3.3V,EN=VIN,Vo1=10V,T A=-40°C to85°C,typical values are at T A=25°C(unless otherwise noted)

(1)With V in=supply voltage of the TPS65140,Vo4=output voltage of the regulator,V BE=basis emitter voltage of external transistor.

(2)The power good goes high when all3outputs(Vo1,Vo2,Vo3)are above their threshold.The power good goes low as soon as one of

the outputs is below their threshold.

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TPS65140TPS65145

SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

DEVICE INFORMATION (continued)

Terminal Functions

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C1−

C1+

Vo3

C2+

C2−

ENR BASE FB4

REF

FB2

DRV

COMP

FB1

VIN

FB3

PG

GND GND PGND PGND

SUP

EN

TPS65145

SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

FUNCTIONAL BLOCK DIAGRAM

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TYPICAL CHARACTERISTICS

Table of Graphs

I L − Load Current − mA E f f i c i e n c y − %

I L − Load Current − mA E f f i c i e n c y − %

707580

859095

V I − Input Voltage − V

E f f i c i e n c y − %

TPS65145

SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

EFFICIENCY

EFFICIENCY

EFFICIENCY

vs

vs

vs

LOAD CURRENT

LOAD CURRENT

INPUT VOLTAGE

Figure 1.Figure 2.Figure 3.

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V SW 10 V/div

V O

50 mV/div

V I = 3.3 V

V O = 10 V/300 mA

I L 1 A/div 250 ns/div

− N −C h a n n e l M a i n S w i t c h −m ΩT A − Free-Air Temperature − °C

r D S (o n )

−40

−20020406080100

T A − Free-Air Temperature − °C

S w i t c h i n g F r e q u e n c y − M H z

Vo1

200 mV/div V I = 3.3 V

Vo1 = 10 V, C O = 22 µF I O

50 mA to 250 mA

100 µs/div

Vo1

100 mV/div

V I = 3.3 V

Vo1 = 10 V, C O = 2*22 µF

I O

50 mA to 250 mA

100 µs/div

V SW 10 V/div

V O

50 mV/div

V I = 3.3 V

V O = 10 V/10 mA

I L

500 mA/div

250 ns/div

Vo15 V/div

V I = 3.3 V V O = 10 V,I O = 300 mA

500 µs/div

I I 500mA/div

Vo15 V/div V I = 3.3 V V O = 10 V,

500 µs/div

Vo25 V/div

Vo3

10 V/div

Vo1 − Output Voltage − V

− O u t p u t C u r r e n t − A

I O TPS65145

SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

TYPICAL CHARACTERISTICS (continued)

SWITCHING FREQUENCY

r DS(on)N-CHANNEL MAIN SWITCH

vs

vs

PWM OPERATION CONTINUOUS

FREE-AIR TEMPERATURE

FREE-AIR TEMPERATURE

MODE

Figure 4.

Figure 5.

Figure 6.

PWM OPERATION AT LIGHT LOAD

LOAD TRANSIENT RESPONSE

LOAD TRANSIENT RESPONSE

Figure 7.

Figure 8.Figure 9.

POWER-UP SEQUENCING

SOFT START Vo1

Vo2MAXIMUM LOAD CURRENT

Figure 10.Figure 11.Figure 12.

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0.020.040.060.080.100.120.14

Vo1 − Output Voltage − V − O u t p u t C u r r e n t − A

I O 00.02

0.040.060.080.10

0.12

10

11

12

13

14

15

Vo1 − Output Voltage − V

− O u t p u t C u r r e n t − A

I O DETAILED DESCRIPTION

Main Boost Converter

Power-Good Output

Enable and Power-On Sequencing (EN,ENR)

TPS65145

SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

TYPICAL CHARACTERISTICS (continued)

Vo3MAXIMUM LOAD CURRENT

Vo3MAXIMUM LOAD CURRENT

Figure 13.Figure 14.

The TPS65140/45consists of a main boost converter operating with a fixed switching frequency of 1.6MHz to allow for small external components.The boost converter output voltage Vo1is also the input voltage,connected via the pin SUP,for the positive and negative charge pump.The linear regulator controller is independent from this system with its own enable pin.This allows the linear regulator controller to continue to operate while the other supply rails are disabled or in shutdown due to a fault condition on one of their outputs.Refer to the functional block diagram for more information.The main boost converter operates with PWM and a fixed switching frequency of 1.6MHz.The converter uses a unique fast response,voltage mode controller scheme with input voltage feedforward.This achieves excellent line and load regulation (0.2%A load regulation typical)and allows the use of small external components.To add higher flexibility to the selection of external component values,the device uses external loop compensation.Although the boost converter looks like a nonsynchronous boost converter topology operating in discontinuous mode at light load,the TPS65140/45maintains continuous conduction even at light load currents.

This is achieved with a novel architecture using an external Schottky diode and an integrated MOSFET in parallel connected between SW and SUP (see the functional block diagram).The integrated MOSFET Q2allows the inductor current to become negative at light load conditions.For this purpose,a small integrated P-channel MOSFET with typically 10Ωr DS(on)is sufficient.When the inductor current is positive,the external Schottky diode with the lower forward voltage conducts the current.This causes the converter to operate with a fixed frequency in continuous conduction mode over the entire load current range.This avoids the ringing on the switch pin as seen with a standard nonsynchronous boost converter and allows a simpler compensation for the boost converter.

The TPS65140/45has an open-drain power-good output with a maximum sink capability of 1mA.The power-good output goes high as soon as the main boost converter Vo1and the negative and the positive charge pumps are within regulation.The power-good output goes low as soon as one of the outputs is out of regulation.In this case,the device goes into shutdown at the same time.See the electrical characteristics table for the power-good thresholds.

The device has two enable pins.These pins should be terminated and not left floating to prevent faulty operation.Pulling the enable pin (EN)high enables the device and starts the power-on sequencing with the main boost converter Vo1coming up first,then the negative and positive charge pumps.The linear regulator has an independent enable pin (ENR).Pulling this pin low disables the regulator,and pulling this pin high enables this regulator.

Positive Charge Pump Negative Charge Pump Linear Regulator Controller Soft Start

Fault Protection

Thermal Shutdown

TPS65145 SLVS497B–SEPTEMBER2003–REVISED MARCH2004

If the enable pin(EN)is pulled high,the device starts its power-on sequencing.The main boost converter starts up first with its soft start.If the output voltage has reached91.25%of its output voltage,the negative charge pump comes up next.The negative charge pump starts with a soft start and when the output voltage has reached91%of the nominal value,the positive charge pump comes up with the soft start.

Pulling the enable pin low shuts down the device.Dependent on load current and output capacitance,each of the outputs comes down.

The TPS65140/45has a fully regulated integrated positive charge pump generating Vo3.The input voltage for the charge pump is applied to the SUP pin that is equal to the output of the main boost converter Vo1.The charge pump is capable of supplying a minimum load current of20mA.Higher load currents are possible depending on the voltage difference between Vo1and Vo3.See Figure13and Figure14.

The TPS65140/45has a regulated negative charge pump using two external Schottky diodes.The input voltage for the charge pump is applied to the SUP pin that is connected to the output of the main boost converter Vo1. The charge pump inverts the main boost converter output voltage and is capable of supplying a minimum load current of20mA.Higher load currents are possible depending on the voltage difference between Vo1and Vo2. See Figure12.

The TPS65140/45includes a linear regulator controller to generate a3.3-V rail which is useful when the system is powered from a5-V supply.The regulator is independent from the other voltage rails of the device and has its own enable(ENR).

The main boost converter as well as the charge pumps and linear regulator have an internal soft start.This avoids heavy voltage drops at the input voltage rail or at the output of the main boost converter Vo1during start-up caused by high inrush currents.See Figure10and Figure11.

All of the outputs of the TPS65140/45have short-circuit detection and cause the device to go into shutdown.The main boost converter has overvoltage and undervoltage protection.If the output voltage Vo1rises above the overvoltage protection threshold of typically5%of Vo1,then the device stops switching,but remains operational. When the output voltage falls below this threshold,the converter continues operation.When the output voltage falls below the undervoltage protection threshold of typically8.75%of Vo1,because of a short-circuit condition, the TPS65140/45goes into shutdown.Because there is a direct pass from the input to the output through the diode,the short-circuit condition remains.If this condition needs to be avoided,a fuse at the input or an output disconnect using a single transistor and resistor is required.The negative and positive charge pumps have an undervoltage lockout(UVLO)to protect the LCD panel of possible latch-up conditions due to a short-circuit condition or faulty operation.When the negative output voltage is typically above9.5%of its output voltage (closer to ground),then the device enters shutdown.When the positive charge pump output voltage,Vo3,is below8%typical of its output voltage,the device goes into shutdown.See the fault protection thresholds in the electrical characteristics table.The device is enabled by toggling the enable pin(EN)below0.4V or by cycling the input voltage below the UVLO of1.7V.The linear regulator reduces the output current to20mA typical under a short-circuit condition when the output voltage is typically<1V.See the functional block diagram.The linear regulator does not go into shutdown under a short-circuit condition.

A thermal shutdown is implemented to prevent damage due to excessive heat and power dissipation.Typically, the thermal shutdown threshold is160°C.If this temperature is reached,the device goes into shutdown.The device can be enabled by toggling the enable pin to low and back to high or by cycling the input voltage to GND and back to V I again.

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APPLICATION INFORMATION

BOOST CONVERTER DESIGN PROCEDURE

D +

V out V D *V

in V out V D *V sw +10V 0.8V *3.3V 10V 0.8V *0.5V

+0.73I L *I

out 1 D *300mA 1 0.73*1.11A p i L

+ƪV in *V sw Ť D

f s L

+

(3.3V *0.5V) 0.73

1.6MHz 4.2m H

+304mA

I swpeak *I L p i

L 2*1.11A 304mA 2

*1.26A Inductor Selection

TPS65145

SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

The first step in the design procedure is to calculate the maximum possible output current of the main boost converter under certain input and output voltage conditions.Below is an example for a 3.3-V to 10-V conversion:V in =3.3V,V out =10V,Switch voltage drop V sw =0.5V,Schottky diode forward voltage V D =0.8V 1.Duty cycle:

2.Average inductor current:

3.Inductor peak-to-peak ripple current:

4.Peak switch current:

The integrated switch,the inductor,and the external Schottky diode must be able to handle the peak switch current.The calculated peak switch current has to be equal or lower to the minimum N-MOSFET switch current limit as specified in the electrical characteristics table (1.6A for the TPS65140and 0.96A for the TPS65145).If the peak switch current is higher,then the converter cannot support the required load current.This calculation must be done for the minimum input voltage where the peak switch current is highest.The calculation includes conduction losses like switch r DS(on)(0.5V)and diode forward drop voltage losses (0.8V).Additional switching losses,inductor core and winding losses,etc.,require a slightly higher peak switch current in the actual application.The above calculation still allows for a good design and component selection.Several inductors work with the TPS65140.Especially with the external compensation,the performance can be adjusted to the specific application requirements.The main parameter for the inductor selection is the saturation current of the inductor which should be higher than the peak switch current as calculated above with additional margin to cover for heavy load transients and extreme start-up conditions.Another method is to choose the inductor with a saturation current at least as high as the minimum switch current limit of 1.6A for the TPS65140and 0.96A for the TPS65145.The different switch current limits allow selection of a physically smaller inductor when less output current is required.The second important parameter is the inductor dc resistance.Usually,the lower the dc resistance,the higher the efficiency.However,the inductor dc resistance is not the only parameter determining the efficiency.Especially for a boost converter where the inductor is the energy storage element,the type and material of the inductor influences the efficiency as well.Especially at high switching frequencies of 1.6MHz,inductor core losses,proximity effects,and skin effects become more important.Usually,an inductor with a larger form factor yields higher efficiency.The efficiency difference between different inductors can vary between 2%to 10%.For the TPS65140,inductor values between 3.3µH and 6.8µH are a good choice but other values can be used as well.Possible inductors are shown in Table 1.

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Output Capacitor Selection

p V out ƪI out

C out Ť1f s +I p L

V out *V d +V

in

*I p ESR

I p = Peak current as described in the previous section peak current control

L = Selected inductor value I out = Nominal load current f s = Switching frequency

V d = Rectifier diode forward voltage (typically 0.3 V)C out = Selected output capacitor ESR = Output capacitor ESR value

Input Capacitor Selection

Rectifier Diode Selection

TPS65145

SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

APPLICATION INFORMATION (continued)

Table 1.Inductor Selection

For best output voltage filtering,a low ESR output capacitor is recommended.Ceramic capacitors have a low ESR value but depending on the application,tantalum capacitors can be used as well.A 22-µF ceramic output capacitor works for most of the applications.Higher capacitor values can be used to improve load transient regulation.See Table 2for the selection of the output capacitor.The output voltage ripple can be calculated as:

with:

For good input voltage filtering,low ESR ceramic capacitors are recommended.A 22-µF ceramic input capacitor is sufficient for most of applications.For better input voltage filtering,this value can be increased.See Table 2and the typical applications for input capacitor recommendations.

Table 2.Input and Output Capacitors Selection

To achieve high efficiency,a Schottky diode should be used.The voltage rating should be higher than the maximum output voltage of the converter.The average forward current should be equal to the average inductor current of the converter.The main parameter influencing the efficiency of the converter is the forward voltage and the reverse leakage current of the diode;both should be as low as possible.Possible diodes are:On Semiconductor MBRM120L,Microsemi UPS120E,and Fairchild Semiconductor MBRS130L.

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Converter Loop Design and Stability

Design Procedure Quick Steps

Setting the Output Voltage and Selecting the Feedforward Capacitor V out +1.146V ƪ1*R1

R2

Ť

F

V O 1

Up to 10 V/150 mA

C8*12 p f z R1*

12 p 50kHz R1

TPS65145

SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

The TPS65140/45converter loop can be externally compensated and allows access to the internal transconductance error amplifier output at the COMP pin.A small feedforward capacitor across the upper feedback resistor divider speeds up the circuit as well.To test the converter stability and load transient performance of the converter,a load step from 50mA to 250mA is applied and the output voltage of the converter is monitored.Applying load steps to the converter output is a good tool to judge the stability of such a boost converter.

1.Select the feedback resistor divider to set the output voltage.

2.Select the feedforward capacitor to place a zero at 50kHz.

3.Select the compensation capacitor on pin COMP.The smaller the value,the higher the low frequency gain.

4.Use a 50-k Ωpotentiometer in series to C c and monitor V out during load transients.Fine tune the load transient by adjusting the potentiometer.Select a resistor value that comes closest to the potentiometer resistor value.This needs to be done at the highest V in and highest load current because stability is most critical at these conditions.The output voltage is set by the external resistor divider and is calculated as:

Across the upper resistor,a bypass capacitor is required to speed up the circuit during load transients as shown in Figure 15.

Figure 15.Feedforward Capacitor

Together with R1the bypass capacitor C8sets a zero in the control loop at approximately 50kHz:

A value closest to the calculated value should be used.Larger feedforward capacitor values reduce the load regulation of the converter and cause load steps as shown in Figure 16.

Load Step Compensation

f z*1

2p Cc Rc

C C = 4.7 nF

TPS65145 SLVS497B–SEPTEMBER2003–REVISED MARCH2004

Figure16.Load Step Caused By A Too Large Feedforward Capacitor Value

The regulator loop can be compensated by adjusting the external components connected to the COMP pin.The COMP pin is connected to the output of the internal transconductance error amplifier.A typical compensation scheme is shown in Figure17.

Figure17.Compensation Network

The compensation capacitor C c adjusts the low frequency gain,and the resistor value adjusts the high frequency gain.The following formula calculates at what frequency the resistor increases the high frequency gain.

Lower input voltages require a higher gain and a lower compensation capacitor value.A good start is C c=1nF for a3.3-V input and C c=2.2nF for a5-V input.If the device operates over the entire input voltage range from 2.7V to5.8V,a larger compensation capacitor up to10nF is recommended.Figure18shows the load transient with a larger compensation capacitor,and Figure19shows a smaller compensation capacitor.

Figure18.C C=4.7nF

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C C

= 1 nF

TPS65145

SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

Figure 19.C C =1nF

Lastly,R c needs to be selected.A good practice is to use a 50-k Ωpotentiometer and adjust the potentiometer for the best load transient where no oscillations should occur.These tests have to be done at the highest V in and highest load current because the converter stability is most critical under these conditions.Figure 20,Figure 21,and Figure 22show the fine tuning of the loop with R c .

Figure 20.Overcompensated (Damped Oscillation),R C Is Too Large

Figure 21.Undercompensated (Loop Is Too Slow),R C Is Too Small

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V out ƪ+V

REF Ť1*R3R4 *V REF ƪ+1.213V Ť1*R3R4

*1.213V R3ƪR4 ȧȱȲŤV out Ť*V REF V REF +1ȧȳȴ

ƪR4 ŤV out Ť*1.2131.213+1

TPS65145

SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

Figure 22.Optimum,R C Is Ideal

Negative Charge Pump

The negative charge pump provides a regulated output voltage by inverting the main output voltage,Vo1.The negative charge pump output voltage is set with external feedback resistors.

The maximum load current of the negative charge pump depends on the voltage drop across the external Schottky diodes,the internal on resistance of the charge pump MOSFETS Q8and Q9,and the impedance of the flying capacitor,C12.When the voltage drop across these components is larger than the voltage difference from Vo1to Vo2,the charge pump is in drop out,providing the maximum possible output current.Therefore,the higher the voltage difference between Vo1and Vo2,the higher the possible load current.See Figure 12for the possible output current versus boost converter voltage Vo1and the calculations below.Vout min =-(Vo1-2V D -Io (2×r DS(on)Q8+2×r DS(on)Q9+X cfly ))Setting the output voltage:

The lower feedback resistor value,R4,should be in a range between 40k Ωto 120k Ωor the overall feedback

resistance should be within 500k Ωto 1M Ω.Smaller values load the reference too heavy and larger values may cause stability problems.The negative charge pump requires two external Schottky diodes.The peak current rating of the Schottky diode has to be twice the load current of the output.For a 20mA output current,the dual Schottky diode BAT54or similar is a good choice.Positive Charge Pump

The positive charge pump can be operated in a voltage doubler mode or a voltage tripler mode depending on the configuration of the C2+and C2-/MODE pins.Leaving the C2+pin open and connecting C2-/MODE to GND forces the positive charge pump to operate in a voltage doubler mode.If higher output voltages are required the positive charge pump can be operated as a voltage tripler.To operate the charge pump in the voltage tripler mode,a flying capacitor needs to be connected to C2+and C2-/MODE.

The maximum load current of the positive charge pump depends on the voltage drop across the internal Schottky diodes,the internal on-resistance of the charge pump MOSFETS,and the impedance of the flying capacitor.When the voltage drop across these components is larger than the voltage difference Vo1×2to Vo3(doubler mode)or Vo1×3to Vo3(tripler mode),then the charge pump is in dropout,providing the maximum possible output current.Therefore,the higher the voltage difference between Vo1×2(doubler)or Vo1×3(tripler)to Vo3,the higher the possible load current.See Figure 13and Figure 14for output current versus boost converter voltage,Vo1,and the following calculations.Voltage doubler:

Vo3max =2×Vo1-(2V D +2×Io ×(2×r DS(on)Q5+r DS(on)Q3+r DS(on)Q4+X C1))

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V out +1.214 ƪ1*R5

R6Ť

R5+R6

ƪ

V out V FB

*1

Ť

+R6

ƪ

V out 1.214

*1

Ť

TPS65145

SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

Voltage tripler:

Vo3max =3×Vo1-(3×V D +2×Io ×(3×r DS(on)Q5+r DS(on)Q3+r DS(on)Q4+X C1+X C2))The output voltage is set by the external resistor divider and is calculated as:

Linear Regulator Controller

The TPS65100/05includes a linear regulator controller to generate a 3.3-V rail when the system is powered from a 5-V supply.Because an external npn transistor is required,the input voltage of the TPS65140/45applied to VIN needs to be higher than the output voltage of the regulator.To provide a minimum base drive current of 13.5mA,a minimum internal voltage drop of 500mV from V in to V base is required.This can be translated into a minimum input voltage on VIN for a certain output voltage as the following calculation shows:Vin min =Vo4+V BE +0.5V

The base drive current together with the h FE of the external transistor determines the possible output current.Using a standard npn transistor like the BCP68allows an output current of 1A and using the BCP54allows a load current of 337mA for an input voltage of 5V.Other transistors can be used as well,depending on the required output current,power dissipation,and PCB space.The device is stable with a 4.7-µF ceramic output capacitor.Larger output capacitor values can be used to improve the load transient response when higher load currents are required.Thermal Information

An influential component of the thermal performance of a package is board design.To take full advantage of the heat dissipation abilities of the PowerPAD or QFN package with exposed thermal die,a board that acts similar to a heatsink and allows for the use of an exposed (and solderable)deep downset pad should be used.For further information.see Texas Instrumens application notes (SLMA002)PowerPAD Thermally Enhanced Package ,and (SLMA004)Power Pad Made Easy .For the QFN package,see the application report (SLUA271)QFN/SON PCB Attachement .

Layout Considerations

For all switching power supplies,the layout is an important step in the design,especially at high-peak currents and switching frequencies.If the layout is not carefully designed,the regulator might show stability and EMI problems.Therefore,the traces carrying high-switching currents should be routed first using wide and short traces.The input filter capacitor should be placed as close as possible to the input pin VIN of the IC.See the evaluation module (EVM)for a layout example.

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D1L1Vin

Vo1Vo3Good

Vo2

D1L1Vin

Vo1Vo3Good TPS65140TPS65145SLVS497B–SEPTEMBER 2003–REVISED MARCH 2004

Figure 23.Typical Application,Notebook Supply

Figure 24.Typical Application,Monitor Supply

19

THERMAL PAD MECHANICAL DATA PowerPAD™

PLASTIC SMALL-OUTLINE

PACKAGING INFORMATION Orderable Device

Status (1)Package Type Package Drawing Pins Package Qty Eco Plan (2)Lead/Ball Finish MSL Peak Temp (3)TPS65140PWP

ACTIVE HTSSOP PWP 2460None CU NIPDAU Level-1-220C-UNLIM TPS65140PWPR

ACTIVE HTSSOP PWP 242000None CU NIPDAU Level-1-220C-UNLIM TPS65140RGER

ACTIVE QFN RGE 243000None CU NIPDAU Level-2-235C-1YEAR TPS65145PWP

ACTIVE HTSSOP PWP 2460None CU NIPDAU Level-1-220C-UNLIM TPS65145PWPR

ACTIVE HTSSOP PWP 242000None CU NIPDAU Level-1-220C-UNLIM TPS65145RGER

ACTIVE QFN RGE 243000None CU NIPDAU Level-2-235C-1YEAR (1)The marketing status values are defined as follows:

ACTIVE:Product device recommended for new designs.

LIFEBUY:TI has announced that the device will be discontinued,and a lifetime-buy period is in effect.

NRND:Not recommended for new designs.Device is in production to support existing customers,but TI does not recommend using this part in a new design.

PREVIEW:Device has been announced but is not in production.Samples may or may not be available.

OBSOLETE:TI has discontinued the production of the device.

(2)Eco Plan -May not be currently available -please check http://www.ti.com/productcontent for the latest availability information and additional product content details.

None:Not yet available Lead (Pb-Free).

Pb-Free (RoHS):TI's terms "Lead-Free"or "Pb-Free"mean semiconductor products that are compatible with the current RoHS requirements for all 6substances,including the requirement that lead not exceed 0.1%by weight in homogeneous materials.Where designed to be soldered at high temperatures,TI Pb-Free products are suitable for use in specified lead-free processes.

Green (RoHS &no Sb/Br):TI defines "Green"to mean "Pb-Free"and in addition,uses package materials that do not contain halogens,including bromine (Br)or antimony (Sb)above 0.1%of total product weight.

(3)MSL,Peak Temp.--The Moisture Sensitivity Level rating according to the JEDECindustry standard classifications,and peak solder temperature.

Important Information and Disclaimer:The

information provided on this page represents TI's knowledge and belief as of the date that it is provided.TI bases its knowledge and belief on information provided by third parties,and makes no representation or warranty as to the accuracy of such information.Efforts are underway to better integrate information from third parties.TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.TI and TI suppliers consider certain information to be proprietary,and thus CAS numbers and other limited information may not be available for release.

In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s)at issue in this document sold by TI to Customer on an annual basis.

PACKAGE OPTION ADDENDUM

www.ti.com 4-Mar-2005Addendum-Page 1

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TI warrants performance of its hardware products to the specifications applicable at the time of sale in accordance with TI’s standard warranty. T esting and other quality control techniques are used to the extent TI deems necessary to support this warranty. Except where mandated by government requirements, testing of all parameters of each product is not necessarily performed.

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